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Journal of Microwaves, Optoelectronics and Electromagnetic Applications

On-line version ISSN 2179-1074

J. Microw. Optoelectron. Electromagn. Appl. vol.16 no.4 São Caetano do Sul Dec. 2017 


Optimized Limited Size Printed Bowtie Antenna for UHF RFID Readers

Leandro Andrade-Fonseca1 

Adriano C. Lisboa2 

Ricardo Adriano3 

Elson J. Silva3 

1Department of Communications, School of Electrical and Computer Engineering, State University of Campinas, Campinas, São Paulo, Brazil,

2Gaia Solutions on Demand, Belo Horizonte, Minas Gerais, Brazil,

3Department of Electrical Engineering, Federal University of Minas Gerais, Belo Horizonte, Minas Gerais, Brazil,,


A novel design of a printed bowtie antenna without a ground plane and with size below a quarter wavelength for RFID readers is presented. Due to the lack of a ground plane, the designed antenna has omnidirectional characteristics and is insensitive to small permittivity deviations. For matching purposes without introducing gain distortion, a shorting strip connecting the radiating arms and four triangular shaped extensions of the radiating arms are added to the antenna design. Measurements show that operation in the 915 MHz band is met with a bandwidth of 13% (S11 < -10 dB) and gain around 2 dBi, while presenting an omnidirectional radiation pattern. Also, the proposed antenna design can be easily modified to operate at neighboring frequency bands.

Index Terms Printed antennas; UHF; shorting strip; bowtie; RFID

I. Introduction

Radio frequency identification (RFID) systems are adequate for real-time tracking and management of objects and people. Its application ranges from industry production to healthcare systems. Recent trends in logistics and supply chain management require fixed RFID readers with reduced size antennas. Also, in some situations an omnidirectional radiation is desired for this class of readers. The challenge of impedance matching in limited size RFID reader antennas is dealt with several design techniques: replacing radiating elements with artificial transmission lines [1], adopting a microstrip-to-coplanar stripline Marchand balun [2], introducing four tuning stubs and an L-shaped metal strip in a slot antenna [3], with a multi-objective optimization approach [4]. Other size reduction techniques are described in [57].

Alternative antenna designs that ensures low-cost, reduced size, simple geometry, robustness against manufacturing errors and presents an omnidirectional radiation pattern are desired. A suitable approach for this purpose would be a printed bowtie like antenna, since simple improvements can be made for setting up its operating frequency. Indeed, the antenna design proposed in this article is a printed bowtie antenna that complies with its specified size restriction as a consequence of the introduced modifications.

This article presents a novel design of a modified printed bowtie antenna fed by a 50 Ω coaxial line for fixed RFID readers operating from 902 MHz to 928 MHz. In the literature, printed bowtie antennas are sometimes mounted above a ground plane [89]. However, in order to preserve the omnidirectional radiation pattern, which is necessary for some RFID fixed reader applications, the ground plane is discarded in our design. Without a conventional ground plane, the antenna is not sensible to small permittivity deviations and an omnidirectional gain is obtained. As to overcome limitations imposed by coaxial feeding, impedance tuning is attained by adding a shorting strip between its radiating arms and four triangular shaped extensions of the radiating arms. The added modifications does not distort the radiation pattern of the antenna, so that the gain of a regular printed bowtie antenna is preserved. Moreover, the operating band of the antenna can easily be shifted by adjusting the parameters of both the shorting strips and the radiating arms extensions, so that specific UHF RFID frequency bands are managed with few adjustments. Maximum dimensions for this antenna are 0.23λ × 0.23 λ × 0.005λ, where λ is the vacuum wavelength of the center frequency at 915 MHz. Measurements shows operation with S11 < -10 dB in the 915 MHz band with a bandwidth of 13% (858-982 MHz) and gain around 2 dBi, while presenting an omnidirectional radiation pattern.

A. Antenna design workflow

In this work, at first a classical printed bowtie antenna fed by a coaxial line is modeled and optimized. However, as the largest size of the substrate is less than a quarter of the operating wavelength, the desired specifications cannot be achieved. Then, by introducing and adjusting modifications on the geometry of the antenna, considerable low values of VSWR at the operating frequency are obtained, and an omnidirectional gain is accomplished. Introduced modifications does not distort radiation pattern of the antenna, so that the gain of a regular printed bowtie antenna is preserved. Overall, the work-flow of the antenna design is:

  1. Design a classical printed bowtie antenna without a conventional ground plane.

  2. Optimize the classical bowtie antenna.

  3. Introduce a first modification to the classical bowtie antenna: a shorting strip between its radiating arms.

  4. Introduce a second modification to the classical bowtie antenna: four triangular shaped extensions of the radiating arms.

  5. Adjust the parameters of the two introduced modification to improve the antenna performance and handle its specifications.

All computational models were built with Ansys HFSS software [10]. The interface between the optimization method and the HFSS was done through Visual Basic Scripting.

II. Classical Bowtie Design

Initially a classical printed bowtie antenna is designed, as shown in Fig. 1, without a ground plane. Parameterization is also presented in this figure. Note that the conductive part shown in Fig. 1(b) is just an extension of the outer conductor of the coaxial line, used only for feeding purposes. This coaxial line transition acts as a balanced to unbalanced balun impedance matching transformer.

Fig. 1 Classical bowtie design. The white inside the L1 sided box depicts the FR4 substrate, gray depicts conducting parts, black circles depicts via holes for feeding. a) Top View. b) Bottom view. 

The antenna is printed on a FR-4 substrate with dimensions L1 × L1 × h, where h is the substrate thickness, with a dielectric constant εr =4.4 and loss tangent tan δ = 0.02. The dielectric is used for mounting purposes and does not affect the antenna operation considerably. With a 1.6 mm substrate height and a neglected ground plane, the dielectric losses due to the low-cost lossy dielectric adopted are avoided, therefore a high radiation efficiency is ensured. In RFID readers the maximum dimensions for the antenna is a major constraint in the antenna design. Usually less than a quarter of a wavelength is available in the RFID system for the antenna. Here the substrate dimensions are fixed at 75 × 75 × 1.6 mm3 in order to comply with specifications of a fixed RFID reader device under development.

A. Antenna feeding

Although microstrip transmission lines are widely used for feeding printed antennas, microstrip feeding method requires considerable increase in ground plane, which would distort the desired omnidirectional radiation pattern. Recent antenna designs [11, 12] inserts defects in the ground plane for size reduction and to excite additional resonance bands. But, these defects are not applicable in the present design.

For the proposed antenna design, a coaxial transition feeding method was chosen in order to achieve a simple and low-cost design. Furthermore, with this feeding method the ground plane can be neglected. Through two via holes in the substrate, inner and outer conductors of the coaxial line are connected to each radiating arm. Since substrate sides are maintained at approximately 0.23λ, where λ is the vacuum wavelength of the center frequency at 915 MHz, a proper matching with the coaxial line is not straightforward.

B. Classical bowtie optimization

The antenna parameters [L2, W1, W2, S1] are subjected to an optimization problem for maximum VSWR minimization from 900 MHz to 930 MHz. The Differential evolution (DE) algorithm [13] is applied. The optimization problem objective function is the maximum antenna VSWR value in the 900-930 MHz frequency range [4]. With this objective function the best parameters settings can be achieved for operation at the desired frequency range.

After several iterations of the optimization, the best individual achieved maximum VSWR of 6.9 at the operating frequency, which is highly undesired. High VSWR values are caused mainly due to substrate side size restriction. The optimal parameters are L2=35.3 mm, W1=1.2 mm, W2=73 mm, S1=2 mm. The distance from the central point of the antenna to the feeding point, represented as black circles in Fig. 1, is 1.2 mm. Fig. 2 presents return loss simulation in a blue color dashed line, which shows an impedance matching around 1,150 MHz.

Fig. 2 Comparative simulations of return loss for printed bowtie antennas over a large bandwidth. 

It is clear that impedance matching techniques must be applied in order to obtain reasonable values of VSWR at the operating frequency range. Since a feed reshaping is not feasible, the above mentioned matching techniques are not applicable. Therefore, antenna characteristics were improved as described in the following sections, while the antenna bottom face is kept the same as the one shown in Fig. 1(b).

III. Proposed modifications

For a proper impedance matching, a shorting strip between the radiating arms and four triangular shaped extensions of the radiating arms are added to the classical bowtie antenna presented in section II, thus reshaping it. The proposed modified bowtie antenna design is depicted in Fig. 3, where the parameters are enlarged for a better view.

Fig. 3 Proposed antenna design and main parameters. (a) Top view with shorting strip and radiating arms extensions. (b) Bottom view. 

A. Shorting Strip

Close to the gap at the feeding region, a shorting strip is inserted connecting both bowtie radiating arms as shown in Fig. 3. The shorting strip is parameterized by two variables: its distance d1 from the center of the antenna, and its track width W3. By adjusting these parameters, the input impedance Zin of the antenna can be significantly changed. For example, the capacitive coupling generated by the gap that separates both radiating arms of the antenna can be compensated with the shorting strip.

The shorting strip effect on the antenna's input impedance is shown in Fig. 4, in which the capacitive coupling is compensated in almost half of its bandwidth. In this figure the Zin of the classical bow-tie antenna with and without the shorting strip can be compared. In the proposed antenna the shorting strip increases the Re(Zin) and the undesired gap capacitive coupling was reduced in a significant portion of the frequency band.

Fig. 4 Comparative simulations for proposed modifications. (a) Re(Zin), (b) Im(Zin). 

The shorting strip parameters are subjected to a local adjustment for minimizing VSWR, and then are set as d1=2.9 mm and W3=0.3 mm. Simulation of the return loss for the printed bowtie antenna with shorting strip is presented with the color black in Fig. 2. Only by adding this connection, maximum VSWR values decrease from 6.9 to 2.8 at the operating frequency. Furthermore, return loss is shifted towards the desired operating frequency, as shown in the same figure.

Indeed, an improvement was observed with the advent of the shorting strip. However, it is clear that in order to achieve a perfect matching, the return loss must be further shifted towards the operating frequency. Such improvement can be attained by decreasing the Re(Zin).

B. Shorting strips and radiating arms extensions

Aiming to improve the bandwidth of its designed antenna, [2] uses a closely-coupled parasitic element. Differently, [14] reports shorted parasitic elements for bandwidth improvement. Inspired by these, in the present design four triangular shaped elements are inserted close to the outermost vertex of the bowtie antenna, extending its radiating arms.

It was observed through simulation that, in this case, connecting the triangular shaped elements with the radiating arms performs a better impedance matching than detached elements. Additionally, the design complexity is not affected with the new elements directly connected to the radiating arms, only one new degree of freedom is inserted. The radiating arms extensions are parameterized with one parameter only, which is L3, as shown in Fig. 3.

Pursuing to shift the return loss to the desired operating frequency, the L3 parameter is also subjected to a local adjustment for VSWR minimization in the operating frequency bandwidth, which results in L3=16.3 mm.

Simulation of the proposed antenna with both radiating arms extensions and shorting strip is also depicted in Fig. 2 in the red color solid line, with the optimal parameter set. The return loss placement suggests that a proper matching is obtained for the proposed antenna at the desired operating band of 915 MHz. The maximum VSWR value at the 902-928 MHz bandwidth is 1.32, which implies an almost perfect match with the 50 Ω coaxial line. This impedance matching is achieved since the Re(Zin) is shifted to almost 50 Ω through the operating frequency bandwidth due to the radiating arms extensions. Therefore, the shorting strip along with the triangular shaped extensions of the radiating arms are a simple and efficient tool for impedance matching.

C. Final antenna design

So, in the final antenna design the parameters [d1, L3, W3] are adjusted as to attain a perfect impedance matching with the fed line. This is done by experimental test, which is suitable because of few parameters. Finally, the proposed modified bowtie antenna design optimal dimensions are: L1=75 mm, L2=35.3 mm, W1=1.2 mm, W2=73 mm, W3=0.3 mm, S1=2 mm, d1=2.9 mm and L3=16.3 mm.

D. Dealing with FR-4 εr deviation

It is known that the adopted dielectric, FR4, has considerable dielectric constant deviation, depending on its manufacturer. An antenna with εr insensitiveness is desired when a low-cost dielectric is used. However, in this antenna design the substrate is adopted for mounting purpose only, the antenna resonance is not considerably affected by εr deviation. The proposed optimized and modified antenna was simulated thrice with εr =4.2, εr =4.4 and εr =4.6, the results are presented in Fig. 5. This figure shows that there is no significant variation for VSWR values through the operating frequency bandwidth.

Fig. 5 Simulated VSWR of the proposed antenna when the FR-4 εr is varied. 

IV. Easiness of frequency shifting

The UHF RFID frequency band is country dependent, therefore, reader antennas must be easily scalable for specific frequency bands. Some examples of UHF RFID frequency assignments are: Europe (866-869 MHz), North and South America (902-928 MHz) and Japan (950-956 MHz). The operating frequency of the antenna design presented in this paper can be easily shifted by simply adjusting the parameters of both the shorting strip and the triangular shaped extensions, which is a relevant advantage compared to other designs.

Fig. 6 presents some alternative parameters settings for [d1, L3, W3] obtained from simulation. It can be seen that the added modifications can be used to shift the operating band of the antenna for other frequency ranges. Only by setting d1=1.9 mm, L3=30.3 mm and W3=0.3 mm operation at lower frequencies ranges can be achieved. On the other hand, setting d1=6 mm, L3=15 mm and W3=0.5 mm allow the designed antenna to operate in higher frequency bands.

Fig. 6 Comparative simulations of return loss for printed bowtie antennas over a large bandwidth. 

The Table I. below details the simulated bandwidth for the three above mentioned UHF RFID frequency bands. In higher frequencies the impedance matching is broadened since the antenna is electrically larger.

Table I Designed antenna frequency shift 

Frequency Band Bandwidth (%)
867.5 MHz 9.29
915 MHz 6.92
953 MHz 16.26

V. Measured results

In order to fully characterize and verify the designed antenna with its final optimal dimensions, return loss and gain measurements were conducted. The fabricated antenna is shown in Fig. 7.

Fig. 7 Photograph of the fabricated antenna, where the light green region depicts the conductive parts. The shorting strip is the thin line between the radiating arms. (a) Top view, (b) bottom view. 

Fig. 8 shows a good agreement between return loss simulation (S11) and measurement. The simulated bandwidth with S11 < -10 dB is 9.29% (875-960 MHz), while the measured bandwidth is 13.55% (858-952 MHz). Fig. 9 presents gain radiation pattern simulation and measurement, which confirms the expected antenna performance. Approximately 2 dBi peak gain was observed in measurement, which is in compliance with the simulated one. Omnidirectional gain is observed at the zx-plane, attending specifications for a fixed RFID reader.

Fig. 8 Return loss simulation and measurement. 

Fig. 9 Simulated and measured radiation patterns for the proposed modified bowtie antenna. The simulation is in color red with a line, and the measurement is in color black with lines and point markers. 

VI. Conclusion

A novel design of a printed bowtie antenna is proposed, in which the conventional ground plane that occupies one face of the substrate is removed. Therefore, an omnidirectional gain is achieved. The antenna design is not sensitive to εr since the substrate is used mainly for mounting purposes. The proposed combined alterations of shorting strip and radiating arms extensions for impedance matching improved the antenna as desired, without changing its size and feeding method. Another advantage of the antenna design presented is that by simply adjusting parameters of the added modifications, operation at specific RFID bands and other frequency bands can be achieved. Also, gain characteristics of the respective regular printed bowtie antenna were preserved. Furthermore, the novel proposed combined method for matching does not increase design complexity. Therefore antenna production cost is kept almost the same of a regular printed bowtie antenna.


This work was supported by CNPq, CAPES and FAPEMIG, Brazil.


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Received: June 15, 2017; Revised: June 26, 2017; Accepted: September 27, 2017

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